View U210B1_1330089.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

U210B1
Phase Control Circuit-Load Current Feedback Applications
Description
The interated circuit, U210B1, is designed as a phasecontrol circuit for load-current feedback application in bipolar technology. To realize motor control systems, it has integrated load current detection, voltage monitoring and soft-start functions. The voltage obtained due to load current proportionality, can be used according to the application i.e., load-current compensation or loadcurrent regulation.
Features
D D D D D
Externally controlled integrated amplifier Variable soft start Automatic retriggering Voltage and current synchronization Triggering pulse typ. 125 mA Package: DIP14
D Internal supply voltage monitoring D Temperature constant reference source D Current requirement 3 mA
14 Voltage detector
1 Current detector Automatic retriggering Output pulse 4
5 Control amplifier 6
8
+ -
7
Phase control unit o = f (V12)
3 Supply voltage limitation Reference voltage Voltage monitoring 2 13
-VS GND
Load current detection
Soft start
12
11
9
10
95 10686
Figure 1. Block diagram
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
1 (12)
U210B1
2 (12)
1N4007 D1 R1 M L 18 kW 1.5 W R3 220 kW
95 10693
R4 470 kW 1 Current detector Output pulse 5 6 3 Supply voltage limitation Reference voltage Voltage monitoring R 2 220 k W 10 nF C2 2 -VS 13 GND C1 C5 50 mW R8 100 W Automatic retriggering 4 R 12 BTA 12-800 VM = 230 V
14 Voltage detector
R9 10 kW
Set speed voltage
X
R6 4.7 kW 8 + 7 - Control amplifier
R7 100 k W
C9
2.2 mF/ 16 V
Phase control unit o = f (V12 )
1 mF/ 16 V
22 mF/ 25 V
N
Load current detector Soft start 12 2 kW C3 220 nF R5 C4 11 9 10
Figure 2. Block diagram with external circuitry Open loop control with load current compensation 10 mF/ 16 V
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
U210B1
Description
Mains Supply
The U210B1 is fitted with voltage limiting and can therefore be supplied directly from the mains. The supply voltage between Pin 2 (+pol/ ) and Pin 3 builds up across D1 and R1 and is smoothed by C1. The vaIue of the series resistance can be approximated using: R1= VM-VS 2 IS When the potential on Pin 6 reaches the nominal value predetermined at Pin 9, then a trigger pulse is generated whose width tp is determined by the value of C2 (the value of C2 and hence the pulse width can be evaluated by assuming 8 ms/nF). At the same time, a latch is set, so that as long as the automatic retriggering has not been activated, then no more pulses can be generated in that half cycle. The current sensor on Pin 1 ensures that, for operation with inductive loads, no pulse will be generated in a new half cycle as long as current from the previous half cycle is still flowing in the opposite direction to the supply voltage at that instant. This makes sure that "Gaps" in the load current are prevented. The control signal on Pin 9 can be in the range 0 V to -7 V (reference point Pin 2). If V9 = -7 V then the phase angle is at maximum = amax i .e. the current flow angle is a minimum. The minimum phase angle amin is when V9 = V2.
Further information regarding the design of the mains supply can be found in the data sheets in the appendix. The reference voltage source on Pin 13 of typ. -8.9 V is derived from the supply voltage. It represents the reference level of the control unit. Operation using an externally stabiIised dc voltage is not recommended. If the supply cannot be taken directly from the mains because the power dissipation in R1 would be too large, then the circuit shown in the following figure 3 should be employed. ~
Voltage Monitoring
As the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveillance. At the same time, all of the latches in the circuit (phase control, soft start) are reset and the soft-start capacitor is short circuited. Used with a switching hysteresis of 300 mV, this system guarantees defined start-up behaviour each time the supply voltage is switched on or after short interruptions of the mains supply.
24 V~
1 2 3 4 5
R1
C1
95 10362
Soft-Start
As soon as the supply voltage builds up (t1), the integrated soft-start is initiated. The figure below shows the behavior of the voltage across the soft-start capacitor and is identical with the voltage on the phase control input on Pin 9. This behaviour allows a gentle start-up for the motor. C4 is first charged with typ. 30 mA. The charging current then increases as the voltage across C4 increases giving a progressively rising charging function with more and more strongly accelerates the motor with increasing rotational speed. The charging function determines the acceleration up to the set point. The charging current can have a maximum value of 85 mA.
Figure 3. Supply voltage for high current requirements
Phase Control
The function of the phase control is largely identical to that of the well known component TEA1007. The phase angle of the trigger pulse is derived by comparing the ramp voltage, which is mains synchronized by the voltage detector, with the set value on the control input Pin 9. The slope of the ramp is determined by C2 and its charging current. The charging current can be varied using R2 on Pin 5. The maximum phase angle amax can also be adjusted using R2.
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
3 (12)
U210B1
96 11565
V10 V9
Pulse Output Stage
The pulse output stage is short circuit protected and can typically deliver currents of 125 mA. For the design of smaller triggering currents, the function IGT = f (RGT) has been given in the data sheets in the appendix. In contrast to the TEA1007, the pulse output stage of the U210B1 has no gate bypass resistor.
Automatic Retriggering
The automatic retriggering prevents half cycles without current flow, even if the triac is turned off earlier e.g., due to not exactly centred collector (brush lifter) or in the event of unsuccessful triggering. After a time lapse of tpp = 4.5 tp is generated another triggering pulse which is repeated until either the triac fires or the half cycle finishes.
t t1 t2 ttot
General Hints and Explanation of Terms
Figure 4. Soft-start
To ensure safe and trouble-free operation, the following points should be taken into consideration when circuits are being constructed or in the design of printed boards.
t1 t2 ttot
= build-up of supply voltage = run-up time = total start-up time to required speed
D The connecting lines from C2 to Pin 6 and Pin 2 should
be as short as possible, and the connection to Pin 2 should not carry any additional high current such as the load current. When selecting C2, a low temperature coefficient is desirable.
95 10716
Control Amplifier
The integrated control amplifier with differential input has a bipolar current output, with typically 110 mA at Pin 9 and a transmittance of typ. 1000 mA/V. The amplification and frequency response are determined by external circuit. For operation as a power control, it should be connected with Pin 7. Phase angle of the firing pulse can be adjusted by using the voltage at Pin 8. An internal limiting circuit prevents the voltage on Pin 9 becoming more negative than V13 + 1 V.
V Mains Supply
p/2
p
3/2p
2p
VGT Trigger Pulse VL Load Voltage
tp
tpp = 4.5 tp
Load Current Detection, Figure 2
Voltage drop across R8, dependent of load current, generates an input-current at Pin 11 limited by R5. Proportional output current of 0.44 x I11 (CTR) is available at Pin 12. It is proportional with respect to phase and amplitude of load current. Capacitor C3 integrates the current whereas resistor R7 evaluates it. The voltage obtained due to load current proportionality, can be used according to the application i.e., load current compensation or load current regulation.
IL Load Current
o F
Figure 5. Explanation of terms in phase relationship
4 (12)
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
U210B1
Absolute Maximum Ratings
Reference point Pin 2, unless otherwise specified Parameters Current requirement q t 10 ms Synchronisation current t 10 ms t 10 ms Load current monitoring Input current Phase control Input voltage Input current Soft-start Input voltage Pulse output Reverse voltage Amplifier Input voltage Reference voltage source Output current Storage temperature range Junction temperature Ambient temperature range Pin 1 Pin 14 Pin 1 Pin 14 Pin 11 Pin 11 Pin 9 Pin 9 Pin 5 Pin 10 Pin 4 Pin 8 Pin 7 Pin 13 Pin 3 Symbol -IS -is -Isync.I -Isync.V -iI Value 30 100 5 5 35 35 2 5 0 to 7 500 1
jV
Unit mA mA
"i
v
t 10 ms
-II -II
mA
"I
-VI
I -II
V
mA
mA V V
-VI Vo VI -VI Io Tstg Tj Tamb
13j
to 0
VS to 5 0 to VS 13j to 0
jV
V mA C C C
7.5 -40 to +125 125 -10 to +100
Thermal Resistance
Parameters Junction ambient DIP14 Symbol RthJA Value 120 Unit K/W
Electrical Characteristics
-Vs = 13 V, Tamb = 25C, reference point Pin 2, unless otherwise specified Parameters Supply voltage for mains operations Supply voltage limitation DC supply current Reference voltage source Temperature coefficient Voltage monitoring Turn-on threshold Turn-off threshold TELEFUNKEN Semiconductors Rev. A1, 28-May-96 Test Conditions / Pins Pin 3 -IS = 3 mA -IS = 30 mA -VS =13 V -IL = 10 mA -IL = 5 mA Pin 3 Pin 3 Pin 13 Pin 13 Pin 3 Pin 3 Symbol -VS -VS -IS -VRef -TCVRef -VSON -VSOFF Min. 13.0 14.6 14.7 1.2 8.6 8.3 Typ. Max. VLimit 16.6 16.8 3.0 9.2 9.1 Unit V V mA V mV/K 13.0 V V 5 (12)
2.5 8.9 0.5 11.2 10.9
9.9
U210B1
Parameters Phase control currents Current synchronization Voltage synchronization Voltage limitation Reference ramp, figure 6 Load current Ro-reference voltage Temperature coefficient Pulse output, figure 11 Output pulse current Reverse current Output pulse width Automatic retriggering Repetition rate Amplifier Common mode voltage range Input bias current Input offset voltage Output current Test Conditions / Pins Pin 1 Pin 14 Pin 1 Pin 14 Symbol Isync.I Isync.V Min. 0.35 0.35 8.0 8.0 Typ. Max. 3.5 3.5 9.5 9.5 Unit mA V
IS= 5 mA
"V "V
I I
8.9 8.9
I6 = f(RF) Figure 6 Rf = 1 K ... 820 KW Pin 6 a 180 Pin5,3 Pin 5 RGT= 0, VGT=1.2 V Pin 4 Pin 4 Co = 10 nF Pin4,2 Pin 4 Pin7,8 Pin 8 Pin7,8 Pin 9
I6 VoRef TCVoRef Io Ior tp tpp V7,8 IIB VIO -IO +IO Yf
1 1.06
1.13 0.5 125 0.01 80 4.5
20 1.18
mA
V mV/K mA
100
150 3.0
mA ms
tp V
3 V13
6 -1
Figure 9
75 88
Short circuit forward trans- I12 = f(V10-11) Pin 9 mittance Soft-start, figures 7, 8 Pin 10 Starting current V10 = V13 Final current V10 = -0.5 V Discharge current, restart pulse Load current detection, figure 10 Pin 11 Input current voltage VI = 300 mV, R1 = 1 KW Input offset voltage Output open current Output current Current transfer ratio I 12 CTR I 11 VI = 0 V, R1= 1 KW Pin 12 VI = 300 mV, R1 = 1 KW V12 = V13 Pin 12 I12 = 150 mA Pin 12/11 Pin 12/11 I12 = 300 mA Pin 12/11
0.01 13 110 120 1000
1 145 165
mA
mV
mA
mA/V mA mA
mA
IO IO -IO
20 50 0.5
30 85 3
50 130 10
II II VIO IO IO CTR
0 300 -8 1.9 120 127 0.44 5% 0.42 6% 0.2
500 308 0 5.5 134
mA mA
mV
mA mA
+
Temperature coefficient of current transfer ratio
TC
0/ /K 00
6 (12)
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
U210B1
240 Phase Control Reference Point Pin 2 200 ( ) 10nF 4.7nF I 9 ( mA ) 2.2nF 160 100 Control Amplifier 50
Phase Angle
a
0
120 -50 80 0 0 0.2 0.4 0.6 0.8 1.0
96 11615
C o/t=1.5nF -100 Reference Point Pin 13 -200 -100 0 V7-8 ( V ) 100 200 300
-300
95 10302
Ro ( MW )
Figure 6.
100 Soft Start 80 I 10 ( mA ) 400 500 R5=100W
Figure 9.
Reference Point for: I12 Pin 13, VR8 Pin 2 500W I12 ( mA )
220W
60
300 1kW 200 100 0 0 0.15 0.3 0.45 0.6 0.75 2kW
40 20 f/V-Converter non-active Reference Point Pin 13 0 0
96 11616
2
4
6 V10 ( V )
8
10
95 10336
V(R8) ( V )
Figure 7.
10 100
Figure 10.
Pulse Output
8 Soft Start 6 I GT ( mA ) V10 ( V )
80
60
4 2 f/V-Converter non-active Reference Point Pin 13 0
96 11617
40 20 0 0
1.4V
VGT = 0.8V
200
400
t=f(C4)
95 10313
RGT ( W )
600
800
1000
Figure 8.
Figure 11.
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
7 (12)
U210B1
50 40 Mains Supply R 1( kW ) 30
Design Calculations for Mains Supply
The following equations can be used for the evaluation of the series resistor R1 for worst case conditions: R 1max
20 10 0 0 4 8 Itot ( mA ) 12 16
P (R1max)
+ 0.85 V 2 -I V + (V 2 -RV )
Mmin tot Mmax Smin 1
Smax
R 1min
+ V 2 -I V
M
Smin
Smax
2
95 10315
Figure 12.
6 5 Mains Supply P(R1) ( W ) 4 3 2 1 0 0
95 10316
where: VM = Mains voltage, 230 VX VS = Supply voltage on Pin 3 = Total DC current requirement of the circuit Itot = ISmax + Ip + Ix ISmax = Current requirement of the IC in mA = Average current requirement of the triggering Ip pulses = Current requirement of other peripheral Ix components R1 can be easily evaluated from the diagrams figures 12 to 14.
10
20 R1 ( kW )
30
40
Figure 13.
6 5 Mains Supply P(R1) ( W ) 4 3 2 1 0 0
95 10317
3
6
9
12
15
Itot ( mA )
Figure 14.
8 (12)
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
U210B1
Applications
In contrast to simple speed controller, the circuits shown in figures 15 and 16, react to the load dependent speed drop in which the magnitude of the load current acts on the speed compensation. For this purpose, the load current is measured by shunt resistor R8. The voltage drop generates a current at Pin 11 dependent of R5, which reflects in the specified current at the output of Pin 12. Rated impedance of the output current at Pin 12 is represented through the coupling resistance R7 and the total impedance of the set point. The integrated load current proportional signal at C3 effects in the same direction on the control input as the set point i.e., by the increase of load current follows an automatic increase of manipulated set point, so that a compensation of speed falls. Compensation arrangement is influenced with resistance values i.e. R5 (= 100 to 5 kW) and R7 (= 10 kW to 150 kW) whereas the higher effect is achieved by increasing the value of R7 and decreasing R5. Influence of compensation can be increased up to the value where the drive system (motor) starts to oscillate. Dimensioning in the applications are with the drill machine of 700 W power. R6 L 230 V~ N M D1 1N4004 R3 220 kW 220 nF C3 C4 15 mF 10 V R7 T1 BC308B R15 10 kW 4.7 kW min max
22 kW
R10 100 kW 11 10 9 8
14 R1 18 kW 1.5 W
13
12
R5 2 kW
U210B
95 10786
1 R4 BTA 12-800 R8 50 mW C1 470 kW 100 W R12
2
3
4 R2
5
6
7
220 kW
22 mF 25 V
C2
10 nF
Figure 15. Speed control with load current compensation
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
9 (12)
U210B1
R6 L 230 V~ N M R3 220 kW D1 1N4004 C3 220 nF C4 15 mF 10 V 14 R1 18 kW 1.5 W 13 12 11 10 9 8 6.8 kW R7 20 kW R11 100 kW R15 min 220 kW max R10 10 kW
1 R4 BTA 12-800 R8 50 mW C1 470 kW R12 22 mF 25 V 100 W
2
3
4 R2
5
6
7
220 kW
C2
10 nF
Figure 16. Speed control with load current compensation
10 (12)
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
95 10787
R5 2 kW
U210B
U210B1
L 230 V~ N Load R3 220 kW C3 470 nF R6 330 kW C4 4.7 mF 10 V R7 2.2 kW C5 C6 P1
D1 1N4004
15 mF 10 V 14 13 12 11
min 100 kW max R9 47 kW
0.1 mF 9 8
10
1 R4 470 kW BTA 12-800 R8 50 mW C1 22 mF 25 V R12 100 kW
2
3
4 R2
5
6
7
220 kW
C
10 nF
Figure 17. Load current regulation with soft start
Current regulation is achieved by the integrated operational amplifier as P1-controller (R7, C5, C6). Inverted input (Pin 7) of the operational amplifier is directly connected at C3 with load current proportional test signal
(actual value). Desired value is obtained with the help of potentiometer at Pin 8.
Dimensions in mm
Package: DIP14
94 9445
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
95 10788
R1 18 kW 1.5 W
R5 2 kW
U210B
11 (12)
U210B1
Ozone Depleting Substances Policy Statement
It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to 1. Meet all present and future national and international statutory requirements. 2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances ( ODSs). The Montreal Protocol ( 1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances. TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents. 1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively 2 . Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency ( EPA) in the USA 3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C ( transitional substances ) respectively. TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances.
We reserve the right to make changes to improve technical design and may do so without further notice. Parameters can vary in different applications. All operating parameters must be validated for each customer application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany Telephone: 49 ( 0 ) 7131 67 2831, Fax number: 49 ( 0 ) 7131 67 2423
12 (12)
TELEFUNKEN Semiconductors Rev. A1, 28-May-96

▲Up To Search▲

Price & Availability of U210B1

	To Download U210B1 Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .